• 专利附录
  • 专利说明
  • 权利要求
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    • 专利摘要:
    Lidar system with suppressed doppler frequency shift. That reduces or suppresses the frequency change induced by the movement of objects in relation to the LIDAR, comprising a light source, an entrance aperture (101), a divider (2) to divide a reflected light in a reference channel (4) and a first imaging channel (3), a first imaging optical receiver (5) to obtain a first interference signal, a reference optical receiver (6) to obtain a reference interference signal, an imaging oscillator (111), to be temporarily coherent with the reflected light, a mixer (12), connected to the first imaging optical receiver (5) and to the reference optical receiver (6) to obtain a first intermodulation product with a higher frequency and an intermodulation product of interest with scaled Doppler shift. (Machine-translation by Google Translate, not legally binding)
    公开号:ES2868473A1
    申请号:ES202030326
    申请日:2020-04-21
    公开日:2021-10-21
    发明作者:Balbás Eduardo Margallo
    申请人:Mouro Labs S L；
    IPC主号:
    专利说明:

    [0004] OBJECT OF THE INVENTION
    [0006] The object of the invention is a LIDAR system that makes it possible to reduce or completely suppress the frequency change induced by the movement of objects in a scene in relation to the LIDAR, an effect known as Doppler frequency shift.
    [0008] BACKGROUND OF THE INVENTION
    [0010] A Light Detection and Ranging (LIDAR) device creates a distance map to a target by illuminating the target with laser light and measuring the reflected light with a sensor. Differences in laser light properties, including total round-trip times, phase, or wavelength, can be used to make 3D digital representations of the target.
    [0012] LIDARs are commonly used for high resolution mapping, with applications in geodesy, geomatics, archeology, geography, geology, geomorphology, seismology, forestry, atmospheric physics, laser guidance, aerial laser scan mapping (ALSM), and laser altimetry. The technology is also used in control and navigation for some autonomous vehicles.
    [0014] Some LIDARs make use of what is known as consistent detection. In this detection scheme, the light reflected in the sample is mixed with a local oscillator that is coherent with the reflected light. This approach has several advantages, such as the optical gain that allows the sensitivity of a single photon and allows the use of changes in the phase and wavelength of light to measure distance.
    [0016] A common problem that appears when making use of this type of LIDAR is the frequency shift induced by the movement of objects in the scene relative to the device, an effect known as Doppler frequency shift. Such frequency changes can be large in relation to the bandwidth of the signals used to measure the relevant properties of objects and can complicate extraction. of such relevant data. The present problem becomes of great importance if the relative speed of the objects is significant, as in the case of vehicles, aircraft or satellites.
    [0018] This change in frequency is variable and often unknown, and can widen the bandwidth of the detected signals very significantly. In the case of land vehicles, the relative speed can reach 300 km / h or more. This relative velocity corresponds to a Doppler frequency shift of 54.0 MHz for illumination of A = 1.55 pm. This variable frequency shift complicates the electronic reading and signal processing chain of systems that rely on coherent detection of the target signal.
    [0020] Even if the signal chain can still be handled for a small number of channels, it increases the cost, size and complexity of the final LIDAR system. In addition, it poses a major obstacle to the practical implementation of the coherent multichannel LIDAR system with a large number of inputs.
    [0022] There have been various approaches to solve the problem explained, including one that employs non-uniform sampling or other compressed detection schemes to reduce the overall data rate of the signals.
    [0024] In general, all the approaches developed have the same drawbacks: complex electronic readout circuitry and general signal processing chain, making them expensive, large in size, and generally difficult to implement and scale for multi-channel architectures with large numbers. channels.
    [0026] DESCRIPTION OF THE INVENTION
    [0028] The LIDAR system object of the present invention describes a modification of a coherent LIDAR system that makes use of one or more inlet openings, and that is simple in its implementation. Its goal is to reduce or completely eliminate the frequency shift induced by the motion of objects in a scene relative to LIDAR, an effect known as Doppler frequency shift.
    [0030] In the invention, the reduction or elimination of the frequency shift is performed by measuring the shifted Doppler signal in a reference channel and then making use of the mathematical properties of time domain signal mixing, changing the frequency of one or more imaging channels to cancel or reduce said Doppler shift.
    [0032] Specifically, the suppressed Doppler frequency shift light detection and measurement (LIDAR) system of the present invention comprises at least one light source configured to emit a first light, directed at an external object. The first light is reflected diffusely or specularly on the object and is then received at at least one entrance aperture, thus being a reflected light.
    [0034] The reflected light can be divided into a splitter, positioned downstream of the at least one entrance aperture, the splitter configured to split the reflected light into a reference channel and at least a first imaging channel.
    [0036] Next, a portion of the divided reflected light is guided through the at least one first imaging channel to a first optical imaging IQ receiver (in-phase and quadrature, In-Phase Quadrature-Phase) associated with the first imaging channel. The first optical imaging receiver IQ is configured to obtain a first interference signal comprising a first in-phase component and a first quadrature component.
    [0038] Furthermore, another part of the reflected light is guided through the reference channel to a reference optical IQ receiver associated with the reference channel. The reference optical IQ receiver is configured to obtain a reference interference signal comprising a reference in-phase component and a reference quadrature component.
    [0040] At least one local optical oscillator is associated with the first imaging optical IQ receiver and the reference optical IQ receiver and is configured to be temporally coherent with reflected light.
    [0042] Finally, in one embodiment, the system comprises at least one mixer, connected to the first optical imaging IQ receiver and to the reference optical IQ receiver, and configured to obtain a first intermodulation product with a higher frequency and a second intermodulation product of interest in which its Doppler shift is scaled or completely eliminated.
    [0043] The system described above is a possible embodiment of the present invention. However, the system may comprise a reference aperture and several inlet apertures, or a reference channel and a plurality of imaging channels associated with one or more inlet apertures. The system can also comprise a single local optical oscillator associated with all the optical IQ receivers, or a reference optical local oscillator associated with the reference optical IQ receiver and an imaging local optical oscillator associated with the reference optical IQ receivers, or a reference optical local oscillator associated with the reference optical IQ receiver, and several imaging local optical oscillators, each associated with one or more imaging optical IQ receivers.
    [0045] The system may also comprise an optical amplitude and / or phase modulator applied to the imaging local optical oscillators, such that the generation of intermodulation products occurs directly at the photodetector without the need for electronic mixing.
    [0047] DESCRIPTION OF THE DRAWINGS
    [0049] To complement the description that is made and in order to help a better understanding of the characteristics of the invention, according to a preferred example of a practical embodiment thereof, a set of drawings is attached as an integral part of said description in which, by way of illustration and not limitation, the following has been represented.
    [0051] Figure 1A.- Shows a diagram of the input aperture, the optical IQ receivers and the local optical reference and imaging oscillators in an embodiment of the invention.
    [0053] Figure 1B.- Shows an alternative implementation in which 2x4 MMIs are used for the optical IQ receivers.
    [0055] Figure 2.- Shows a diagram of the LIDAR system in an embodiment of the invention with a reference channel and an imaging channel.
    [0057] Figure 3.- Shows a diagram of the LIDAR system in an embodiment of the invention with a reference channel and a matrix of imaging channels with address information encoded in the relative phase between them.
    [0059] Figure 4.- Shows a diagram of the LIDAR system in an embodiment of the invention with a plurality of input openings and an amplitude modulator for direct mixing of the reference signal in the photodetectors.
    [0061] Figure 5.- Shows two diagrams of a Gilbert cell, one that includes photodetectors to allow direct multiplication of the differential photocurrent.
    [0063] Figure 6.- Shows an integration scheme of a Gilbert cell, using switched capacitors.
    [0065] PREFERRED EMBODIMENT OF THE INVENTION
    [0067] With the aid of Figures 1A to 6, the preferred embodiments of the present invention are described below.
    [0069] The invention relates to a LIDAR system comprising at least one light source configured to emit a first light, directed at an external object. The first light is reflected off the object and then received at a reference entry aperture (102) and an imaging entry aperture (101) in a first embodiment of the invention, being a reflected light.
    [0071] The reference input aperture (102) allows a reference interference signal to be produced between the reflected light from the scene and a reference oscillator (112). This reference interference signal is used to modulate an interference signal formed between the reflected light coming from the scene collected by the imaging input aperture (101) and an imaging oscillator (111).
    [0073] In any given implementation, the reference input aperture (102) and that of the image input aperture (s) (101) may overlap, as shown, for example, in the embodiment of Figure 1A, as well as the oscillator reference (112) and imaging oscillators (111).
    [0075] It is important to the invention that the reference oscillator (112) and the reference oscillator imaging (111) show some degree of temporal coherence with the reflected light, such that the interference signal formed can be processed at electrical frequencies.
    [0077] In an exemplary implementation, shown in Figure 1A, the system comprises a single inlet opening (101,102). In this case, the system comprises a light source, which emits a light directed at an object. The light is reflected off the object and the reflected light, which enters the system through the inlet aperture (101,102) is divided into a first imaging channel (3) and a reference channel (4) by a 1x2 divider (2).
    [0079] It is important for the invention that the at least two channels, the reference channel (4) and the first imaging channel (3), are affected by the movement of the objects through the change in Doppler frequency substantially of the same way, while the non-Doppler information-bearing modulation remains different between them. This allows them to be combined in such a way that the Doppler frequency shift is eliminated or greatly reduced, while recovering the information-bearing modulation.
    [0081] As shown in FIG. 1A, the first imaging channel (3) is fed to a first imaging optical IQ receiver (5), and the reference channel (4) is fed to an imaging optical IQ receiver (5). reference (6). The first optical imaging receiver (5) is associated with an imaging oscillator (111) and the optical reference receiver (6) is associated with a reference oscillator (112). Within the optical IQ receivers (5, 6), both oscillators (111, 112) are fed through 90 ° hybrids that generate the necessary phase shift between the in-phase component (7, 9) and the quadrature component. (8, 10) of each channel.
    [0083] In other embodiments, IQ receivers (5, 6) could be implemented by means of 2x4 MMI (Multi Mode Interference ) couplers designed to provide the required phase shifts between the 4 outputs (7, 8, 9, 10 ) and each of the two inputs (3, 4). In Figure 1B an embodiment is shown in which the first imaging optical IQ receiver (5) is a 2x4 MMI coupler that is fed with the first imaging channel (3) and an imaging oscillator. (111), and the reference optical IQ receiver (6) is a 2x4 MMI coupler that is powered by the reference channel (4) and a reference oscillator (112).
    [0085] In one embodiment, the imaging oscillator (111) has its wavelength swept following a conventional FMCW (Frequency Modulated Continuous Wave) scheme and the reference oscillator (112) maintains its wavelength. static. For this implementation to work, it is important that the reflected light have components that are consistent with both components in the oscillators (111, 112). For this, the lighting must be derived from a combination of both components, or both components must share a common origin with the lighting that guarantees mutual coherence.
    [0087] The first optical imaging IQ receiver (5) is associated with the first imaging channel (3) and is configured to obtain a first interference signal comprising a first in-phase component (7) and a first quadrature component (8). The optical reference IQ receiver (6) is associated with the reference channel (4) and configured to obtain a reference interference signal comprising a reference phase component (9) and a reference quadrature component (10).
    [0089] Both interfering signals will be affected by the Doppler effect in substantially the same way (with small differences due to different wavelengths, in some embodiments). However, only the first interference signal, associated with the imaging oscillator (111), carries information about the distance of the object to the LIDAR system at its interference frequency.
    [0091] The mixing of both signals, the first interference signal and the reference signal, in at least one mixer (12), results in the generation of two intermodulation products: a first intermodulation product with a higher frequency that can be discarded, and an output intermodulation product (16) with a lower frequency, which has its Doppler shift significantly scaled, and which provides the possibility of bringing the measurement information and amplitude to the baseband, and thus minimizing the sampling frequency and the complexity of electronic reading.
    [0093] For example, the first interference signal and the reference interference signal for this implementation are derived below. It is assumed that the opening of Imaging inlet 101 and reference aperture 102 are in substantially the same position, except for possible relative phase shifts if imaging inlet 101 is part of an array. In the case of equal illumination of the scene with two light sources of two wavelengths (with associated wave numbers and angular frequencies k1, k 2 and &>2> respectively) and equal amplitude A, the light signal a a distance x from the light source is:
    [0097] where it is assumed that the first wavelength of the first light source of the LIDAR system is subjected to a linear frequency modulation with constant K. If the object that reflects the light emitted by the first light source is a single diffuse reflector, the object, at a distance x, with reflectivity of intensity p, in the direction of the entrance aperture (101) and the relative velocity in the direction between the entrance aperture (101) and the object vj , the reflected field of the light collected at the inlet opening (101) will be:
    [0102] where í is the index of the input opening in the case that there is an array of them. The Doppler shift is visible in the terms 2 k1vj and 2 k2vj in the equations, modifying the frequency of the reflected light.
    [0104] For the calculation of interference signals in optical IQ receivers (5, 6), it is assumed for simplicity that the two wavelength components of the imaging and reference oscillators (111, 112) have an amplitude of Unit:
    [0106] EX i (t) = [e - j (^ itn K t 2+ ^ 1) ]
    [0108] Ex2 (t) = e -AW2t 02)
    [0110] After the imaging optical IQ receiver (5) and the reference optical IQ receiver (6), the first interference signal and the reference interference signal are, respectively:
    [0113] In these, the shake products where the difference in optical angular frequencies persists will be at a very high frequency by electrical standards once detected. For example, assuming that the two wavelengths of light from light sources are 0.1 nm apart at a wavelength of 1.55 pm, the intermodulation product has a frequency of 12.5 GHz:
    [0118] conversely, beat products where the local oscillator and reflected light frequencies are equal, are demodulated to a lower frequency, derived from the difference in frequency between the emitted and received phase modulation frequency plus or minus the Doppler shift.
    [0120] For the typical speed of ground vehicles, the Doppler shift will be equal to or less than 100 MHz, so it is possible to suppress the higher frequency mixing terms (those that include the difference in optical angular frequencies) by means of a low pass filter. Therefore, as shown in figure 2, a first set of low-pass filters (13) can be associated with the optical IQ receivers (5, 6) in order to filter the first in-phase component (7), the first component in quadrature (8), the component in reference phase (9) and the component in reference quadrature (10).
    [0122] In the following, we will only focus on the low-frequency components of the interfering signals:
    [0125] The depth and velocity information is encoded in the frequency (and phase) of both photocurrents. If we focus only on the frequency information, we see that the frequencies of It ( t) and / 2 (t) are:
    [0130] the components of these two frequency changes are scaled differently with line speed. The modulation constant K has a direct impact on the distance-derived frequencies. However, the Doppler shift remains independent and is determined solely by the properties of the scene. Since the Doppler shift can go up at frequencies of several tens of MHz, it requires fast acquisition electronics, which can add to the cost of the system. These video frequencies are also a problem when it comes to scaling up scene detection with multiple parallel imaging channels (3).
    [0132] However, we note that the difference of these two frequencies is:
    [0137] If the two wavelengths of the lights emitted by the two light sources are chosen to be close to each other (for example, 0.1 nm apart at 1.55 pm wavelength), the difference of the Doppler frequency changes are significantly reduced (2 kHz for a v¡ of 50m / s).
    [0139] However, it is noteworthy that both wavelengths can be the same. In this case, the Doppler shift is totally suppressed, while the frequency shift due to FMCW is preserved. This approach simplifies the necessary optical system and associated electro-optical circuitry.
    [0140] If both wavelengths are equal, the Doppler shift is completely suppressed and the frequency of the signal moves to the baseband. This lower Doppler frequency allows for a significant reduction in line speed, data throughput, and hardware complexity in systems where a large number of input apertures are desired (101). If the Doppler frequency is conserved and needs to be measured, there needs to be a way to disambiguate the Doppler shift from the FMCW modulation. One way to achieve this is to change K in the FMCW frequency sweep over time, for example by alternating its sign, and comparing the resulting electrical frequency changes between both modulation slopes.
    [0142] One way to subtract the frequencies obtained from the optical IQ receivers (5, 6) above is to multiply one of the currents with the complex conjugate of the other. Conventional frequency mixing techniques can be applied. This can be done in the digital or analog domain and potentially on the basis of interfering signals as follows:
    [0144] fl (0 * ^ (0 - Un * Uí + hq * hq) + i Un * ¡ 2 q hq * Uí)
    [0146] In one embodiment, this can be implemented, as shown in Figure 2, using one or more mixers (12) connected to the first imaging optical IQ (5) and to the reference optical IQ outputs (6) or to the first outputs low pass filter assembly (13). Each of the four multiplicative terms above contains a first intermodulation product with the difference in frequencies A / (low frequency) and a second intermodulation product that includes the addition of the Doppler frequencies 2v, (- -).
    [0148] When the four multiplicative terms are combined, the terms related to the addition of Doppler frequencies cancel out, and only the low-frequency intermodulation products, which contain the depth information at their frequency (as by A / above), remain as products. output intermodulation (16).
    [0150] Alternatively, as an alternative, you can filter the highest frequency component of each of the multiplicative terms using a second set of low-pass filters (23) and keep only the low-frequency intermodulation products, which contain the depth information. in its frequency (as per A f above), as output intermodulation products (16).
    [0152] In the embodiment shown in figure 2, the mixer (s) (12) comprise:
    [0153] - a first mixer (121), designed to mix the first quadrature component (8) and the reference phase component (9), providing the multiplicative term ( Ilq * l 2i), and
    [0154] - a second mixer (122), intended to mix the first component in phase (7) and the component in reference phase (9), providing the multiplicative term (71¿ * I2i).
    [0156] In an alternative demodulation technique, it is possible to work with the individual components of the interference signals, that is, the first component in phase (7), the first component in quadrature (8) and those derived from the reference interference signals, as provided by a time shunt module (15): the time derivative of the reference phase component (90) and the time derivative of the reference quadrature component (91), and adapt FM demodulation techniques that simultaneously perform baseband conversion and demodulation.
    [0158] This can be specifically useful in realizations where both the imaging oscillator and the reference oscillator are the same, since in that situation the frequency difference in the multiplicative terms as expressed above would be A f = 0, and the use of Time Derivatives allows the extraction of frequency-coded depth information for the amplitude of the time-derived signals.
    [0160] For example, the operation that can be performed in one or more mixers (12) in this case, in which the imaging and reference oscillator are the same, is:
    [0162] I lQ ÍO h / (O - I iÁ O hq íO = p jA ÍX jft [2 k1Vj + 2 Eos (0 ¿)
    [0163] ¡U iO h / (O - I iQ ( t) I2Q ( t) = p] A ( xj [ 2 k1v¡ + 2 If n (0¿)
    [0165] In a similar way to the direct frequency mixing approach, in this case the previous four multiplicative terms can be generated and combined to leave only the DC component, or alternatively the frequency component can be filtered the most. high of each of the multiplicative terms using a second set of low pass filters (23) and keep only the DC components that contain the depth and Doppler information in their amplitude.
    [0167] To separate the Doppler and depth information, K in the FMCW frequency sweep can be changed over time, for example, by alternating its sign, and comparing the resulting DC component changes between both modulation slopes.
    [0169] One drawback of direct FM demodulation is the fact that the reflectivity of the object ( pj ) and the frequency shift are mixed at this DC value. This can be addressed by demodulating the amplitude separately:
    [0174] Alternatively, in cases where the imaging and reference oscillators are the same, the reflectivity of the object can also be obtained from the multiplicative terms between the signal components and the reference components before the derivative in time ( for example, as provided by the first mixer (121) and the second mixer (122) in Figure 2).
    [0176] For the use of the direct FM demodulation approach, figure 2 shows a time shunt module (15) and one or more mixers comprising:
    [0177] - a third mixer (123), designed to mix the first component in phase (7) and the reference quadrature component derived in time (91), and - a fourth mixer (124), designed to mix the first component in quadrature (8) and the time-derived reference quadrature component (91).
    [0179] Therefore, the embodiment in Figure 2 shows a demodulation scheme that provides frequency and amplitude demodulation simultaneously.
    [0181] Figure 3 shows an implementation where multiple imaging channels (3) are combined with a common reference channel (4) obtained from a reflected light that comes from the same scene, but mixed with a separate optical source (a of a different wavelength but that is consistent with at least a fraction of the power collected from the scene).
    [0183] The advantage of the scheme shown in figure 3 is that the different imaging channels (3) retain the relative phase difference (contained in the IQ data) in the electrical domain after demodulation. This allows the coherent combination of the demodulated signals coming from said imaging channels (3) in order to recover the different directions.
    [0185] For the mixers (12), it is possible to use different construction schemes. In particular, they can be implemented in the analog domain on the basis of circuits that are based on a translinear scheme. One such circuit is the Gilbert cell, which is depicted in Figure 5. This circuit has the advantage of operating in all four quadrants of interfering signals.
    [0187] Since the inputs to the cell are always differential and voltage-based, the photocurrents from the optical IQ receivers (5, 6) above must be amplified by a transimpedance amplifier (14) to a voltage and, if applicable, derived in the analog domain. This adds complexity to the circuitry and makes the scheme more difficult to implement when the number of channels increases.
    [0189] In order to simplify the Gilbert cell, it is possible to use the photocurrents of a balanced differential pair as a source of both input and current bias signals. This will reduce the need for intermediate transimpedance amplifiers and make the cell more susceptible to replication for large-scale integration. The imaging oscillator (111) for mixing with the different image channels (3, 4) can be generated and distributed as a voltage signal over the detection matrix from a single imaging input aperture (101) without major scalability issues.
    [0191] To simplify the reading of the cell, integration schemes with switched capacitors and multiplexed video outputs can be applied as shown in figure 6. The reading of said switched capacitors can be structured in the same way as normal imaging sensors, organizing them by column and using the usual multiplexing schemes to route the analog values to the appropriate ADC circuitry.
    [0192] Finally, in order to provide the desired mixing function, it is also possible to modulate the amplitude of the optical local oscillator going to the imaging channels. If this is done, no electronic mixing is required after photodetection, with obvious advantages in terms of system complexity. For this, an optical modulator (17) can be used, as shown in figure 4. In one embodiment, the optical modulator (17) is an optical amplitude modulator, either based on electro-optical absorption, in a Mach-Zehnder interferometer in another way.
    [0194] If the amplitude modulation leaves a certain level of phase modulation, a series phase modulator can be added to ensure constant phase operation and avoid unwanted frequency shifts in the reference channel. Amplitude modulation can also be obtained in different ways, such as through an optical amplifier, modulation of a laser current, etc.
    [0196] In some embodiments, the first in-phase component (7), the first quadrature component (8), the reference in-phase component (9), and the reference quadrature component (10) would need to be multiplied with different versions of the signal, shifted 90 ° to each other in order to achieve the desired mathematical result directly. To physically accomplish this, this would require the distribution of separately modulated reference signals to each output mixer (12). Although possible, this would complicate the design and signal routing in the device, especially since the phase relationship between both modulated reference optical oscillators must be precisely determined.
    [0198] However, given the fact that the modulation to be applied to these two channels is also orthogonal in the electrical domain, it is possible, in some embodiments, to add them together in the modulation signal, as shown in figure 4.
    [0200] The products between the first in-phase component (7) and the first quadrature component (8) or between the reference in-phase component (9) and the reference quadrature component (10) only produce high-frequency intermodulation products that they can be initially filtered.
    [0202] In order to separate the amplitude and distance information, it is possible to switch the modulation signal applied to the optical modulator (17) between different modes (with or without a time derivative) in such a way that as an alternative the information from depth and / or signal amplitude.
    [0204] This simple time domain multiplexing, which is suitable for implementation with an integrator that is synchronized with the demodulation signal switching, can also be replaced by other multiplexing schemes (frequency domain multiplexing, code multiplexing, etc. .).
    [0206] Figure 4 shows the combination of the two implementation options described above, the Doppler frequency demodulation by means of the amplitude modulation of the optical reference signal and the time multiplexing of the amplitude / frequency demodulation, for the case of a single wavelength.
    权利要求:
    Claims (22)
    [1]
    1. - Light detection and measurement system (LIDAR) with suppressed Doppler frequency shift, comprising:
    - at least one light source configured to emit a first light,
    - at least one imaging input aperture (101) and an imaging channel (3) associated with the at least one imaging input aperture (101), configured to receive input reflected light that is reflected on a moving object irradiated by the at least one light source,
    - at least one reference aperture (102) and a reference channel (4) associated with the at least one reference aperture (102), configured to receive a reference reflected light that is reflected on the moving object irradiated by the light source,
    - at least one imaging oscillator (111),
    - at least one first optical imaging receiver (5) associated with the imaging input aperture (101) and the imaging oscillator (111) and configured to obtain an interference signal between the reflected light from input and the imaging oscillator (111), - a reference oscillator (112),
    - a reference optical receiver (6) associated with the reference aperture (101) and the reference oscillator (112) and configured to obtain a reference interference signal between the reference reflected light and the reference oscillator (112) ,
    - at least one mixer (12), connected to the at least one first optical imaging receiver (5) and to the optical reference receiver (6) and configured to produce an intermodulation product (16) between the interference signal and the reference interference signal, such that the Doppler frequency shift caused by the moving object is canceled or decreased.
    [2]
    2. - The LIDAR system of claim 1, wherein the at least one first optical imaging receiver (5) is an optical IQ receiver configured to obtain an interference signal between the input reflected light and the oscillator of imaging (111) comprising a first in-phase component (7) and a first quadrature component (8), and the reference optical receiver (6) is an IQ receiver optical configured to obtain a reference interference signal comprising a reference phase component (9) and a reference quadrature component (10).
    [3]
    3. - The LIDAR system of claim 2, further comprising a time derivation module (15), associated with the reference optical receiver (6) and destined to derivative in time the reference phase component (9) and the reference quadrature component (10).
    [4]
    4. - The LIDAR system of claim 2, wherein the at least one mixer (12) comprises:
    - a first mixer (121), intended to mix the first quadrature component (8) and the reference phase component (9),
    - a second mixer (122), intended to mix the first component in phase (7) and the component in reference phase (9).
    [5]
    5. - The LIDAR system of claim 2, wherein the at least one mixer (12) comprises:
    - a first mixer (121), intended to mix the first quadrature component (8) and the reference quadrature component (10),
    - a second mixer (122), intended to mix the first component in phase (7) and the reference quadrature component (10).
    [6]
    6. - The LIDAR system of claim 2, wherein the at least one mixer (12) comprises:
    - a third mixer (123), designed to mix the first component in phase (7) and the reference quadrature component derived in time (91), and - a fourth mixer (124), designed to mix the first component in quadrature (8) and the time-derived reference quadrature component (91).
    [7]
    7. - The LIDAR system of claim 2, wherein the at least one mixer (12) comprises:
    - a third mixer (123), designed to mix the first component in phase (7) and the reference phase component derived in time (90), and
    - a fourth mixer (124), intended to mix the first component in quadrature (8) and the reference phase component derived in time (90).
    [8]
    8. - The LIDAR system of any of claims 4 to 7, further comprising a low pass filter (23) associated with each mixer (12).
    [9]
    9. - The LIDAR system of claim 1, wherein the reference oscillator (112) and the imaging oscillator (111) share a common origin.
    [10]
    10. - The LIDAR system of claim 1, wherein the reference aperture (102) is the same as the inlet aperture (101), and the reference channel (4) and the imaging channel (3 ) are derived from it by means of a divisor (2).
    [11]
    11. - The LIDAR system of claim 1, in which the wavelength of the reference oscillator (112) remains static and the wavelength of the first optical oscillator (111) is scanned following an FMCW scheme (modulated continuous wave in frequency) conventional.
    [12]
    12. - The LIDAR system of claim 1, further comprising one or more low-pass filters (13), associated with the optical receivers (5, 6) and intended to filter the interference signal and the reference interference signal , eliminating very high frequencies.
    [13]
    13. - The LIDAR system of claim 2, further comprising transimpedance amplifiers (14) placed after the optical reference receiver (6) and the first optical imaging receiver (5), intended to amplify the component in reference phase (9), the reference quadrature component (10), the first in-phase component (7) and the first quadrature component
    ( 8 ).
    [14]
    14. - The LIDAR system of any of claims 1, 4 to 7, in which the mixers (12) are Gilbert cells.
    [15]
    15. - A LIDAR system that includes:
    - at least one light source configured to emit a first light,
    - at least one imaging inlet opening (101) and an imaging channel (3) associated with the at least one inlet opening imaging device (101), configured to receive input reflected light that is reflected off a moving object radiated by the light source,
    - at least one reference aperture (102) and a reference channel (4) associated with the at least one reference aperture (102), configured to receive a reference reflected light that is reflected on the moving object irradiated by the light source,
    - at least one imaging oscillator (111),
    - at least one first optical imaging receiver (5) associated with the imaging input aperture (101) and the imaging oscillator (111) and configured to obtain an interference signal between the reflected light from input and the imaging oscillator (111), - a reference oscillator (112),
    - a reference optical receiver (6) associated with the reference aperture (101) and the reference oscillator (112) and configured to obtain a reference interference signal between the reference reflected light and the reference oscillator (112) ,
    - an optical modulator (17) connected to the at least one imaging oscillator (111), and configured to apply an amplitude or phase modulation to the imaging oscillator (111) with a signal derived from the signal channel reference (4), such that an intermodulation product (16) between the interference signal and the reference interference signal appears at the output of the at least one first optical imaging receiver (5), in such a way The Doppler frequency shift caused by the moving object is canceled or decreased.
    [16]
    16. - The LIDAR system of claim 15, wherein the at least one first optical imaging receiver (5) is an optical IQ receiver configured to obtain an interference signal between the input reflected light and the input oscillator. imaging (111) comprising a first in-phase component (7) and a first quadrature component (8), and the optical reference receiver (6) is an optical IQ receiver configured to obtain a reference interference signal that It comprises a reference phase component (9) and a reference quadrature component (10).
    [17]
    17. - The LIDAR system of claim 15, wherein the reference oscillator (112) and the imaging oscillator (111) share a common origin.
    [18]
    18. - The LIDAR system of claim 15, wherein the reference aperture (102) is the same as the inlet aperture (101), and the reference channel (4) and the imaging channel (3 ) are derived from it by means of a divisor (2).
    [19]
    19. - The LIDAR system of claim 15, in which the wavelength of the reference oscillator (112) remains static and the wavelength of the first optical oscillator (111) is scanned following an FMCW scheme (modulated continuous wave in frequency) conventional.
    [20]
    20. - The LIDAR system of claim 15, further comprising one or more low-pass filters (13), associated with the optical receivers (5, 6) and intended to filter the interference signal and the reference interference signal , eliminating very high frequencies.
    [21]
    21. - The LIDAR system of claim 16, further comprising transimpedance amplifiers (14) placed after the optical reference receiver (6) and the first optical imaging receiver (5), intended to amplify the component in reference phase (9), the reference quadrature component (10), the first in-phase component (7) and the first quadrature component (8).
    [22]
    22. - Method to suppress the change in Doppler frequency in a LIDAR system, which makes use of the system of any of the preceding claims, and comprises the steps of:
    - emit a first light, directed at a moving object,
    - receive a reflected light from the moving object,
    - obtaining a first interference signal between the reflected light and an imaging oscillator (111),
    - obtain a reference interference signal between the reflected light and a reference oscillator (112),
    - Obtain an intermodulation product (16) between the interference signal and the reference interference signal, in such a way that the change in Doppler frequency caused by the moving object is canceled or decreased.
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    同族专利:
    公开号 | 公开日
    WO2021214135A1|2021-10-28|
    ES2868473B2|2022-02-28|
    引用文献:
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    PCT/EP2021/060383| WO2021214135A1|2020-04-21|2021-04-21|Lidar system with supressed doppler frequency shift|
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